## Thursday, September 30, 2010

### Hi-Tech C vs mikroC Pro

Just out of curiosity I compiled a small sample program on Hi-Tech C for PIC18 v9.63L3 and mikroC Pro v4.10 freeware version. Target MCU was a PIC18F2321. Hi-Tech was used within Microchip's MPLAB IDE v.8.30. Hi-Tech's Omniscient Code Generation (OCG) is on (for the duration of the 45-day eval period). I set the mikroC optimization level to 5 (the maximum).

According to the compilers the Hi-Tech version took up 84 bytes of Flash while the mikroC required 122 bytes. Both compilers used only 2 bytes of RAM. Apparently Hi-Tech wins by a mile, at least in this particular test.

Here's the C program I fed both compilers:

#define  int8    unsigned char

void InitRegisters()
{
IRCF1 = 1;

PORTA = 0;
PORTB = 0;
PORTC = 0;
TRISA = 0;
TRISB = 0;
TRISC = 0;
}

{
}

{
*greens = 0;
}

// ====================================================================
//     main
// ====================================================================

void main()
{
InitRegisters();

while(1)
{
if (PORTC)
else
}  // while (1)
}  // main


Here's the disaasembly listing by Hi-Tech:
1:                 /*
2:
3:                 sandbox
4:                 compiler = Hi Tech
5:
6:                 */
7:
8:                 #include
9:
10:                __CONFIG (1, INTIO & FCMDIS & IESODIS);
11:                __CONFIG (2, PWRTDIS & BORDIS & WDTDIS & WDTPS4);
12:                __CONFIG (3, PBDIGITAL & LPT1DIS & MCLRDIS);
13:                __CONFIG (4, XINSTDIS & STVRDIS & LVPDIS & DEBUGDIS);
14:                __CONFIG (5, 0xFFFF);                                      // write protect disabled
15:                __CONFIG (6, 0xFFFF);            // write protect disabled
16:                __CONFIG (7, 0xFFFF);                                      // write protect disabled
17:
18:
19:                #define  int8    unsigned char
20:
21:                // ====================================================================
22:                //     Global variables and enumerations
23:                // ====================================================================
24:
25:
26:
27:
28:                // ====================================================================
29:                //      Functions
30:                // ====================================================================
31:
32:                void InitRegisters()
33:                {
34:                  IRCF1 = 1;
1FC8    8AD3     BSF 0xfd3, 0x5, ACCESS
1FCA    0E0F     MOVLW 0xf
1FCC    6EC1     MOVWF 0xfc1, ACCESS
36:
37:                  PORTA = 0;
1FCE    6A80     CLRF 0xf80, ACCESS
38:                  PORTB = 0;
1FD0    6A81     CLRF 0xf81, ACCESS
39:                  PORTC = 0;
1FD2    6A82     CLRF 0xf82, ACCESS
40:                  TRISA = 0;
1FD4    6A92     CLRF 0xf92, ACCESS
41:                  TRISB = 0;
1FD6    6A93     CLRF 0xf93, ACCESS
42:                  TRISC = 0;
1FD8    6A94     CLRF 0xf94, ACCESS
43:                }
1FDA    0012     RETURN 0
44:
46:                {
1FBC    C000     MOVFF 0, 0xfe9
1FBE    FFE9     NOP
1FC0    C001     MOVFF 0x1, 0xfea
1FC2    FFEA     NOP
1FC4    68EF     SETF 0xfef, ACCESS
48:                }
1FC6    0CFF     RETLW 0xff
49:
51:                {
52:                  *greens = 0;
1FB0    C000     MOVFF 0, 0xfe9
1FB2    FFE9     NOP
1FB4    C001     MOVFF 0x1, 0xfea
1FB6    FFEA     NOP
1FB8    6AEF     CLRF 0xfef, ACCESS
53:                }
1FBA    0C00     RETLW 0
54:
55:                // ====================================================================
56:                //     main
57:                // ====================================================================
58:
59:                void main()
60:                {
61:                  InitRegisters();
1FDC    ECE4     CALL 0x1fc8, 0
1FDE    F00F     NOP
62:
63:                  while(1)
1FFE    D7F0     BRA 0x1fe0
64:                  {
65:                    if (PORTC)
1FE0    5082     MOVF 0xf82, W, ACCESS
1FE2    E007     BZ 0x1ff2
1FE4    0E82     MOVLW 0x82
1FE6    6E00     MOVWF 0, ACCESS
1FE8    0E0F     MOVLW 0xf
1FEA    6E01     MOVWF 0x1, ACCESS
1FEC    ECD8     CALL 0x1fb0, 0
1FEE    F00F     NOP
1FF0    D7F7     BRA 0x1fe0
67:                    else
1FF2    0E82     MOVLW 0x82


Disassembly listing by mikroC:
;  LST file generated by mikroListExporter - v.2.0
; Date/Time: 9/30/2010 8:21:34 PM
;----------------------------------------------

0x0000        0xF000EF2D          GOTO        90
0x0004        0x0000              NOP
0x0006        0x0000              NOP
0x0008        0xF000EF00          GOTO        0
0x000C        0x0000              NOP
0x000E        0x0000              NOP
0x0010        0x0000              NOP
0x0012        0x0000              NOP
0x0014        0x0000              NOP
0x0016        0x0000              NOP
0x0018        0xD7F3              BRA         0
0x0024        0x0EFF              MOVLW       255
0x0026        0x6EE6              MOVWF       POSTINC1
;sandbox18F.c,39 ::                 }
0x0028        0x0012              RETURN      0
___CC2DW:
;__Lib_System.c,21 ::
;__Lib_System.c,23 ::
_CC2DL_Loop1:
;__Lib_System.c,24 ::
0x002A        0x0009              TBLRD*+
;__Lib_System.c,25 ::
0x002C        0xFFE6CFF5          MOVFF       TABLAT, POSTINC1
;__Lib_System.c,26 ::
0x0030        0x0600              DECF        R0, 1, 0
;__Lib_System.c,27 ::
0x0032        0xE1FB              BNZ         _CC2DL_Loop1
;__Lib_System.c,28 ::
0x0034        0x0601              DECF        R1, 1, 0
;__Lib_System.c,29 ::
0x0036        0xE1F9              BNZ         _CC2DL_Loop1
;__Lib_System.c,31 ::
0x0038        0x0012              RETURN      0
; end of ___CC2DW
;sandbox18F.c,43 ::                 *greens = 0;
0x0042        0x6AE6              CLRF        POSTINC1
;sandbox18F.c,44 ::                 }
0x0044        0x0012              RETURN      0
_InitRegisters:
;sandbox18F.c,23 ::                 void InitRegisters()
;sandbox18F.c,25 ::                 OSCCON.IRCF1 = 1;
0x0048        0x0E0F              MOVLW       15
;sandbox18F.c,28 ::                 PORTA = 0;
0x004C        0x6A80              CLRF        PORTA
;sandbox18F.c,29 ::                 PORTB = 0;
0x004E        0x6A81              CLRF        PORTB
;sandbox18F.c,30 ::                 PORTC = 0;
0x0050        0x6A82              CLRF        PORTC
;sandbox18F.c,31 ::                 TRISA = 0;
0x0052        0x6A92              CLRF        TRISA
;sandbox18F.c,32 ::                 TRISB = 0;
0x0054        0x6A93              CLRF        TRISB
;sandbox18F.c,33 ::                 TRISC = 0;
0x0056        0x6A94              CLRF        TRISC
;sandbox18F.c,34 ::                 }
0x0058        0x0012              RETURN      0
; end of _InitRegisters
_main:
;sandbox18F.c,50 ::                 void main()
;sandbox18F.c,52 ::                 InitRegisters();
0x005A        0xDFF5              RCALL       _InitRegisters
;sandbox18F.c,54 ::                 while(1)
L_main0:
;sandbox18F.c,56 ::                 if (PORTA)
0x005C        0x5280              MOVF        PORTA, 1
0x005E        0xE006              BZ          L_main2
0x0060        0x0E80              MOVLW       PORTA
0x006A        0xD005              BRA         L_main3
L_main2:
0x006C        0x0E80              MOVLW       PORTA
L_main3:
;sandbox18F.c,60 ::                 }  // while (1)
0x0076        0xD7F2              BRA         L_main0
;sandbox18F.c,61 ::                 }  // main
0x0078        0xD7FF              BRA         +0 ; end of _main  ## Tuesday, September 28, 2010 ### The PIC16F1827: an inexpensive, fully loaded MCU I'm excited about the PIC16F1827 because it's packed with peripherals, has five! timers, has an internal clock with a maximum frequency of 32MHz, and yet is no more expensive than other 18pin PIC16s. I want a tube of these! Just my luck though. I'll have to wait. I try and obtain all my PICs from Microchip Direct, but the 1827 won't be available till the end of this year (extended temperature PDIP is on stock, however). RS Components has none either. Farnell has stocks but comes out way pricier. Hardware aside, I have no plans on programming this chip using assembly. So I need a C compiler. You'd expect Microchip's compiler division would have a compiler ready once the chip is out, but even with the acquisition of Hi Tech it has yet to support the 1827. That's rather strange. The just released MikroC Pro v4.10 does support the MCU and several other enhanced PIC16s. BoostC by SourceBoost also recognizes the 1827. Guess I'll be playing with this MCU early next year. ## Friday, September 24, 2010 ### On the blink James Bryant of Analog Devices and his dirty dozen ways for circuits to fail. The PIR circuit I recently installed has been challenging me. Just two days after it was installed it began to at times fail to switch the load on even if the PIR sensor was detecting motion (I know because the LED had turned on, ergo, PIR output was high). The fault was infrequent and usually occurred the first time the pantry was accessed in the morning--circuit must be too groggy to start the day. After days of checking and monitoring supply voltages (and finding nothing wrong with them), I decided to reprogram the MCU. The problem disappeared. Could've been an intermittent contact problem--which was licked when I removed the MCU and reinserted it--or it could've been a bad burn of the firmware. Another problem which was noticed along with the above has yet to be resolved. When the dining room lights are turned off, the pantry light sometimes switches on. This occurs probably once every couple of dozen switchings. Rather obviously transients in the power line from switching off four conventionally ballasted plug-in type 11-watt compact fluorescent lamps are falsely triggering the circuit. I've already monitored MCU VDD using the Min-Max with Peak detect feature of the Fluke 87V for some 24hours and found the voltage to be from 4.930V to 5.048V, so no problem there. On the other hand, given the cable length to the PIR module of some 40cm, the problem may lie there. That's No.5 in Bryant's list. I've been mullling where in the sensor circuit to install additional bypass/decoupling caps. May have to put one at the VDD of the module and another at the MCU input pin (GP3); 0.1 to 1uF for the former and 10 to 100nF for the latter. ## Wednesday, September 22, 2010 ### An important pointer on using mikroC with PIC18s After half a day of trying to get it to work I nearly gave up. Was trying out C pointers using an old version of mikroC on a Microchip PIC18F2321. Here's the test program (to preclude clutter I've removed the initialization routines for OSCCON, PORTx, TRISx, and ADCON1 registers): void OnLoad(unsigned char *salad) { *salad = 0xFF; } void OffLoad(unsigned char *greens) { *greens = 0; } void main() { while(1) { OnLoad(&PORTC); Delay_100ms(); OffLoad(&PORTC); Delay_100ms(); } }  The firware merely toggles PORTC on and off every tenth of a second. An LED is connected to one of the PORTC pins, so it should blink when the MCU is powered up. Well, it didn't work. After a couple of hours of racking my brain and trying out variations on the program, I decided to test the code on a PIC 16F device. I inserted a PIC12F615 into the breadboard, plugged in an LED and resistor, and hooked up the PICKit 2. Opened a new project in mikroC and used the same program, changing PORTx to GPIO, and initializing the appropriate SFRs. Guess what? Worked the first time around. No problems. That told me there's nothing wrong with the program. Went back to the PIC18. After several more hours of checking and hair-pulling, it occured to me that there might be something in the MCU configuration bits which hasn't been set properly. Referring to the datasheet, the only one that seemed relevant was the XINST (Extended Instruction Set enable) bit in configuration word CONFIG4L. Noting that according to the datashet it's off by default, I first enabled it. I compiled the firmware, uploaded to the MCU, and powered it up. Nothing. The program still wouldn't work. Went back to mikroC, unchecked the "XINST_ON_4L" box and checked "XINST_OFF_4L." Hallelujah! The LED finally started blinking, and at the proper rate at that. Finally found the culprit! Just to make sure it was indeed the XINST bit, I enabled it again. Sure enough the program failed again. Disabling XINST once more and the firmware worked. As a final test, I unchecked both these boxes (it was in that condition before I fiddled around with the XINST) and uploaded the compiled code. It didn't work. Therefore, regardless of what Microchip says about the default condition of the configuration words, it is quite clear that they must be explicitly set in mikroC. So there. A nasty little trap which MikroElektronika does not state in their manual. Beware. ## Monday, September 20, 2010 ### Fluke face to face with Kryptonite Australian electronics engineer Dave Jones proves that the Fluke 87V DMM goes haywire in the presence of GSM. Much as I'd like to see this fault for myself, I simply cannot afford to fry my 87V. Instead I used a Fluke 117 as the lab rat. Apparently, the cheapo doesn't even know what a cell phone is. Barely a reaction and not a hint of malfunction. This GSM susceptibility is yet another item in the list of disappointments I have with the 87V. First and foremost is its unforgivably flimsy 9V battery connector. It's no different from those found in China made toys! I cannot imagine how Fluke could have blundered something as basic as this. My old Sanwa DMM had a far more superior battery-compartment-connector system. You unscrew the battery compartment at the back of the meter, remove it, flip it over and insert the battery into it, and then plug the whole thing back into the meter body and screw tight. Once inserted the battery terminals automatically make contact with metal prongs inside the meter. Absolutely great design! Now why couldn't Fluke have made something similar with this model? It's already the Series 5! They certainly did it right on the Fluke 117: Next on the list, and one that puts me off whenever I notice it is the LCD. For some reason Fluke seems to have sacrificed the viewing angle exactly perpendicular to the unit. When looking straight down the segments have rather poor contrast--not as black--as when looking at an angle. At first I thought my unit was faulty, but I've checked another brand new 87V and an 83V and their LCDs both have the same characteristic. And the batteries are still fresh so it's not a low voltage problem. I was never annoyed with the display of my old Sanwa so I guess it didn't have this quirk. Testing the 87V, the LCD is a 6:00 type with a bias angle somewhere between 20 and 30°. The readout is still tolerable even at 60°. ## Sunday, September 12, 2010 ### Pantry light switch using a PIR module Practically all the dry goods in our kitchen are stored in the pantry and we access this room several times a day. My bugbear has been that everyone who uses it, including myself, forgets to turn off the light rather frequently. Something about this tiny room that makes people run in and out less than a minute later and forget to flip the switch. Must the duration of stay inside. Or maybe not, since I also do fail to turn the garage storeroom lights off even if I've been in there for ten minutes. Yeah, must be the genes. Been meaning to install a motion detector to address this problem but couldn't find a readily available PIR in the market. Went to a home depot months ago to buy a consumer security gadget that employed PIR and was going to just hack it. Problem is that when I asked them to test if it's working the dang model didn't. Not a single unit of those tried! What the bleep indeed. Well, fortunately I found an online supplier who had reasonable prices. The module is China-made obviously, but right now I'll take anything over nothing. For details and specs of the passive infrared (PIR) module refer to my previous blog entry. I could've used the module without employing a microcontroller. A transistor and a relay would've been sufficient to switch on the pantry's compact fluorescent lamp (CFL). But that's crude and not at all very user friendly. What happens when the person is still inside and isn't detected by the PIR? Darkness descends without warning. Therefore, there is a need to provide an alert of some sort that it'll be lights out in a while. I would've wanted a visual warning, specifically a PWM controlled lamp that gradually dims. The decreasing light level would be a gentle way of informing the user. But such a circuit is more complicated and I certainly can't dim a CFL. LED high-lumen lighting would be nice, but cost is prohibitive and the drive circuitry complex. So I settled for an audible alert, giving a graduated level of warning as the moment of lamp switch-off approaches. I arbitrarily set the start of warning five seconds before switch-off, with a 10ms beep every second for four seconds. On the last second, a 10ms beep is issued every 200ms for a total of five beeps. The beeps are generated by a small sonalert buzzer but at 10ms they're so short that they sound more like clicks than beeps. My design criterion on this is that the sound level and type should be informative but unobstrusive to those outside the room, so the clicks are on the money. The MCU's job is simply to monitor the PIR module output and switch the CFL accordingly. When PIR output goes high the MCU immediately switches on the CFL, and when it goes low the MCU starts issuing the alert sequence, after which it turns off the lamp. However, since this particular module has an initialization ritual it goes through upon power up, the MCU must also be programmed to disregard the output during this period. Well, the MCU doesn't really have to, but for now I've decided that it should ignore the two PIR output high during initialization since energy is wasted when the CFL on. On the other hand, there is some utility to providing feedback that the PIR is in initialization mode. This can be implemented using the buzzer. A distinct pattern of beeps can be continuously emitted during this period. In anticipation of future PIR module malfunction and of those times when the user would want to keep the light on continuously--i.e., override the sensor--I designed the circuit with a switch to allow the user to turn off auto mode. When in manual mode the CFL will be on regardless of PIR output. The manual override is a surface mount rocker switch rated at 10A @250VAC. Only a feeble current (about half a milliamp DC) will be running through so it'll be dry switching. I'm not worried. Since the MCU won't be doing much at all and will only need a small amount of code, I decided to use a baseline PIC, i.e., a model from the 10F series. The smallest (in Flash memory) chip I have in stock is the PIC10F202. It has four I/O pins which is exactly the number of pins I need. Powering the CFL is via a miniature socketed relay with a 12VDC coil. The Telemecanique RXM2AB2JD is a DPDT switch with contacts rated at 12A @250VAC. As a bonus it has a green LED indicator which is on when the coil is energized. It even has a button which the user can push to momentarily close/open the NO/NC contacts and a mechanical lever to latch them. Love its smart look as well. Thumbs up to this model. To serve as a troubleshooting aid I've added an LED which is switched on by a transistor whenever PIR output is high. The MOSFET is controlled directly by the PIR. Powering the control circuitry is a generic wall cube which has no markings on it. Thankfully this unit isn't one of those whose casing is glued together. It has two screws which allows it to be opened up. As the schematic below shows it has a transformer, bridge rectifier made up of four diodes (can't make out the last digit of any of the 1N400x) and a filter capacitor. Output of the adapter is 19VDC, no load. A LM7812 provides a regulated 12VDC. Although not strictly necessary given the current draw of the circuit, a clip-on anodized aluminum heat sink has been installed on this TO-220 as a precaution. To preclude having too high a voltage headroom, the 78L05 regulator's input is drawn from the output of the LM7812. This reduces the dissipation of the 5VDC regulator. Here are the schematic diagrams and legend to the reference designations. The 10F series of PICs has no interrupt capability and only a 2 level stack for subroutine calls. Pretty spartan indeed, but quite adequate for simple undemanding circuit requirements like this one. I've used the 10F202 for a number of circuits but something I've not learned or already forgotten manage to trip me up. Pretty vexing really. While prototyping I used GP2 as the I/O for the sonalert buzzer. Well, it didn't work! I went over the firmware and it looked good. Took me a long time poring over the datasheet for me to finally discover that GP2 is by default an input pin even if the TRISGPIO2 bit has been correctly set as output. The fact is the TRISIO register has the lowest priority in determining the status of this pin. OSCCAL register FOSC4 bit has the highest priority followed by OPTION register TOCS bit. No problem with FOSC4 since it is upon power up set to zero which means it hands off this pin to other functions. The problem lies with TOCS. It's set to 1 upon any type of reset including power on. And that means the pin is in high impedance mode waiting for a signal. With TOCS set, Timer0 is in counter mode and increments upon a level change (edge trigger) on the GP2 pin. So in order to use this pin as a general I/O TOCS has to be cleared. The 10F202 is practically the most basic MCU in Microchip's line but I have yet to master it. In the end I moved the buzzer to GP1 and used GP2 as an input to sense the status of the auto/manual switch. GP3 is input-only and is used to monitor PIR output. Note that the PIR module works at 3.3VDC and its output high can only reach a maximum of this value. With a VDD of 5V a Schmitt trigger input on the MCU won't be able to detect the PIR high since the minimum requirement for a level high is 80% of VDD, or 4V. Fortunately, when the 10F202 pins are configured as general purpose inputs they are all TTL which has a minimum requirement of only 2.0V to be considered as high. Not so in other cases. For instance when TOCS bit = 1, GP2 becomes a Schmitt trigger input for Timer0 counter. Thus, if we feed the PIR output to this pin, Timer0 would never increment. What the PIR outputs as high would be considered a valid high only if MCU VDD drops to 4.1VDC or less. Firmware consists mainly of a series of polling loops. PIR output is continually monitored while the manual switch is monitored continually only after PIR initialization is complete. When switch SW1 is sensed to be in manual and as long as it is in manual position, PIR is no longer monitored. When SW1 is flipped back to auto position then PIR monitoring resumes. In auto mode and after PIR initialization has been detected to be over, when PIR output goes high, Q2 is immediately turned on which then switches REL on and hence LOAD. When PIR output goes low, the pattern of beeps (as described above) is issued. Five seconds later LOAD is switched off. If PIR output goes high during this five-second waiting time, the alerts stop and firmware exits the alert routine. When user switches from manual to auto mode, firmware checks PIR output to determine whether LOAD will be turned off or not. PIR will almost certainly be high since SW1 is located inside the pantry and in an area right under the PIR, thus making sure the user will be detected while operating the switch. Be that as it may, if PIR output is low then LOAD is turned off, otherwise it is kept on. Currently, there is no routine to issue an audible alert informing the user that the PIR is initializing. There should be. That will probably come in a firmware upgrade. The actual firmware installed is provided below. It's written in MPLAB assembly. Uses only 87 words of flash and 4 bytes of RAM. Watch out! I use homebrew macros and defines throughout. Blogspot truncates any text that extends beyond the margins so if you want to read the code and comments I suggest copying and pasting into a word processor. Or paste it in MPLAB, copy and paste the macros and defines from the above link as well, build it, and read the disassembly listing or "program memory" listing if you're not a huge fan of my macros. Shame on you if you aren't! ; ******************************************** ; Passive Infrared Motion Detector for home panty ; September 2010 ; ; see "PIR sensor.dwg" for schematic ; ********************************************* processor 10F202 #include p10F202.inc #include et.inc __config _MCLRE_OFF & _CP_OFF & _WDT_ON cblock 0x08 CENTISECS ; number of centiseconds for time delay ICOUNTER ; counter for iterations COUNTER:2 ; counters for delays endc #define buz GPIO,0 ; sonalert buzzer #define load GPIO,1 ; switches MOSFET which switches 12VDC relay which switches 220VAC CFL #define sw GPIO,2 ; mode switch: high = manual (load is continuously on), low = auto (motion detect) #define pir GPIO,3 ; PIR output, high = motion detected, low = no motion detected org 0x0 movwf OSCCAL ; load clock calibration goto initialize ; ======================================================================================= ; subroutines ; ; 10F202 can only call subroutines if they are located in first 256 memory locations ; ======================================================================================= ; --------------------------------------------------------------------------------- ; Time delay that's user dependent ; Place number of centiseconds of delay in register CENTISECS before calling this routine DelayCentisec: movlf .164, COUNTER movlf .20, COUNTER+1 delay_loop decfsz COUNTER,f goto delay_loop movlf .164, COUNTER decfsz COUNTER+1,f goto delay_loop clrwdt movlf .20, COUNTER+1 decfsz CENTISECS,f goto delay_loop retlw 0 ; --------------------------------------------------------------------------------- ; --------------------------------------------------------------------------------- ; one centisec beep Beep: bsf buz movlf .1, CENTISECS call DelayCentisec bcf buz retlw 0 ; --------------------------------------------------------------------------------- ; ======================================================================================= ; main program ; ======================================================================================= ; --------------------------------------------------------------------------------- initialize: clrf GPIO movlw b'11011111' ; TOCS bit must be 0 else GP2 will be an input pin; prescaler is assigned to WDT; prescale = 1:2 option movlw b'1100' ; GPIO 0 and 1 are assigned as output, GP2 is input, GP3 is by default an input only pin tris GPIO ; do nothing for about half a second (50 centisec) to give PIR time to initialize and bring its output high movlf .50, CENTISECS call DelayCentisec ; PIR initializes by outputting high twice over a minute or two ; wait until the second falling edge is detected; thereafter any edges detected will be due to normal operation of motion detection ; wait for first PIR falling edge init_pir_loop1 clrwdt dnxtrue pir goto init_pir_loop1 ; wait for PIR rising edge init_pir_loop2 clrwdt dnxfalse pir goto init_pir_loop2 ; wait for second PIR falling edge--signals the end of PIR initialization init_pir_loop3 clrwdt dnxtrue pir goto init_pir_loop3 ; --------------------------------------------------------------------------------- ; --------------------------------------------------------------------------------- main: ; wait for PIR rising edge--which signals that motion has been detected ; check mode sw status clrwdt dnxtrue sw goto manual dnxfalse pir goto main main_motion_true bsf load ; PIR output is high so turn load on main_loop1 ; wait until no motion is detected--until PIR output goes low ; check mode sw status clrwdt dnxtrue sw goto manual dnxtrue pir goto main_loop1 ; PIR output is now low ; give user 5 seconds to activate motion sensor before turning off load ; begin issuing 10ms beep every second for four seconds to alert user that motion is no longer detected ; check PIR output every second; if it goes high (motion is detected) then exit and go to main_loop1 ; check mode sw status every second; if sw level goes high then go to manual mode routine main_motion_false movlf .4, ICOUNTER main_beep_loop0 call Beep movlf .99, CENTISECS call DelayCentisec dnxtrue sw goto manual dnxtrue pir goto main_loop1 decfsz ICOUNTER,f goto main_beep_loop0 ; for the last second issue a 10ms-beep every 200ms ; check PIR output every second; if it goes high (motion is detected) then exit and go to main_loop1 ; check mode sw status every second; if sw level goes high then go to manual mode routine movlf .5, ICOUNTER main_lastsec_beep_loop0 call Beep movlf .19, CENTISECS call DelayCentisec dnxtrue sw goto manual dnxtrue pir goto main_loop1 decfsz ICOUNTER,f goto main_lastsec_beep_loop0 ; if PIR output remains low then turn load off ; go to main whether PIR output is low or high dnxfalse pir bcf load goto main ; manual mode routine ; if sw level is high then turn load on ; if sw level is low and PIR output is low then turn off load ; if sw level is low and PIR output is high then keep load on ; when sw level is low then go to main manual: bsf load manual_loop1 dnxfalse sw goto manual_loop2 clrwdt goto manual_loop1 manual_loop2 dnxfalse pir bcf load goto main end ; ----------------------------------------------------------------------------------  The Installation I need to have control over the area covered/monitored by the PIR sensor but don't have the resources nor the perseverance to build a metal articulated aiming gizmo. Scrounged around and found a round tea can made of cardboard whose slip-on lid could be rotated while it was on. That provides one axis of rotation to aim the the sensor. I could easily bore a hole on the side of the canister and fasten the module with the Fresnel lens sticking out. The lid would then be screwed onto a block of wood which in turn would be bolted to the side panel of the top shelf. If I use just one bolt I can swivel the block. That's the second axis of rotation which would be at right angles to the first. Two planes of swivel is sufficient to aim the sensor practically anywhere. Here are photos of the installation. The first shows the can with the module already in place. I wish I didn't have to glue it to the can but my brain was out of options. The can is actually red. I covered with white paper since the shelves are all white. I don't want it out more than it already will be and calling attention to it. The three wires lead to the circuit board where all the other components are. The lid of the canister is shown fastened to a scrap piece of wood which is epoxied (the black goo) to another piece perpendicular to the former. The latter is bolted to the shelf side panel. The outlet on the pantry wall is newly installed just for this circuit. The thicker SPT cable is 220VAC power line and the smaller gauge SPT leads from the relay to the CFL. The translucent plastic box contains the circuit board and relay In the bottom picture, the circuit is powered and operational. There's the wall wart plugged in with its (newly installed) red and black speaker cable leading to the circuit board inside the plastic box. The wire from the black plug leads to the relay. The white SPT wire along the bottom of the photo leads to the auto-manual switch located several shelves below. You can see I just taped it along the edge of the shelf. In this last photo I am at ground level pointing the camera up. CFL is mounted on the ceiling less than a meter from the module. ### PIR sensor module Recently bought a couple of passive infrared (PIR) modules. The seller lists the part number as DC-SS015, although I can't be certain that this indeed is true. Unfortunately the seller could not provide any datasheet. It may in fact be a SS015 since the pin designations for the headers are the same as those on a datasheet for the DC-SS015 (see below). As far as I can tell there are only two ICs on this module. The SOIC-16 (left of center in the photo) does not have any markings. It could be a BISS001 clone. The (4-pin) SOT-89 (lower right in photo) has ""7533-1" printed on it. I googled and this may be a Holtek 3.3V LDO voltage regulator. The board measures 33mm x 25mm and is marked "Rev1.1." The fresnel lens is hot glued to the board and for now I have not dared remove it for fear of misaligning it. The black circular thingie beneath the board is just a 35mm film canister to the prop the board up. Needed to keep it level with the table while taking the picture given the domed fresnel lens on the other side. Here are screenshots of the pertinent pages from a datasheet I found for the DC-SS015 some time ago. I can no longer find the link for the pdf file by Sure Electronics The position on the board and designation of the header pins of the module match those shown on the datasheet. The 3-pin header at the bottom center of the board (as per the photo above) are for power and output. Left pin (silkscreened "SW") is ground, center pin (marked "OUT") is output, right pin is Vcc. The 3-pin header on the upper left corner has a jumper to select between single trigger and re-triggerable modes. The topmost pin is labeled "H" on the module, while the lowermost pin is labeled "L." With the jumper plugged into the two top pins (H and common) the circuit becomes retriggerable, that is, any motion detected will reset the output high holding period to whatever the user has set it to. With the jumper plugged into the lower two pins (common and L) only the initial motion detected is counted and any further trigger will be ignored until the output-high holding period has elapsed. In other words, in single trigger mode assuming PIR module output is initially low, the time between motion is detected (output goes high) and output goes low is constant. The output-high holding period (for both trigger modes) is user adjustable and is set via a 1Mohm trimmer resistor. That's the orange part on the upper right corner of the board. I've played around with it and the range is from almost zero to 16.75 seconds. The module arrived with the trimmer set at center, which had a measured time of between 9 and 10 seconds. I measured the current draw using a Fluke 87V with its min-max feature turned on. Input voltage was measured at 5.18VDC (using an ATX power supply) and load was a 2N7000 MOSFET with its gate directly connected to the PIR output (no limiting resistor). Minimum current recorded was 37µA while maximum was 98µA. As you can read from the datasheet, quiescent current is specified at 50µA. With the module powered from the same supply as above, output voltage was measured with a Fluke 8842A and for this test module, without any load, low was less than 0.03mV and high = 3.31V. The module has a long initialization time. After powering up output will go high for several seconds, go low for a shorter period of time, high again for several seconds, and then back low. Thereafter, it will be not triggerable for several more seconds. The period for this set up doesn't seem to be fixed, but the whole thing takes about a minute. This unit is able to detect human movement to 4 meters, but sensitivity at that distance is fair at best. Seems to perform well enough within two meters. Angular coverage is apparently greater horizontally (as per board orientation in the photos above) than vertically. Difficult to give precise values, but 90 degrees would be a ballpark figure. I've already used one of the modules in a circuit that automatically switches a compact fluorescent lamp inside a pantry. I'll probably do a blog on that soon. Finally, for a tutorial on PIR devices check out ladyada. ## Saturday, September 4, 2010 ### Adjustable power supply with automatic transformer tap select I'm currently designing and testing a 1-amp power supply based on the good old LM317 voltage regulator. I'd like it to be able to supply a voltage from its minimum of 1.25 V all the way to about 30 V. That's within its specs so no problem with that range. However, one problem is the power dissipation of the 317 which is given by: $P_D = I_{VR} ( V_{IN} - V_{O})$ whereP_D$= power dissipation, in watts$I_{VR}$= current through the voltage regulator, mostly the load current, in amperes$V_{IN}$= input voltage, in volts$V_{O}$= output voltage, in volts The higher the difference between input and output voltage the greater the power loss in the 317. If we use a single input voltage it would have to be at least 33VDC, more likely >35V to factor in capacitor ripple voltage. With an input of 35V and an output of, say, 5VDC headroom would be 30V. If the load were drawing 100mA it would dissipate 5V x 0.1A = 0.5W while the 317 would be wasting 30V x 0.1A = 3W! Without a heatsink and given the thermal resistance of a TO-220 package of around 65°C/W, the junction temperature would well exceed its 125°C maximum. Of course the 317 will probably shut down before reaching that temperature, or it might fry if the thermal overload protection circuitry somehow fails.Not that we wouldn't install a heatsink. It's indispensable for a 1000-mA supply since even with a constant headroom of 3V (minimum required), the regulator would still be dissipating 3W at a current draw of 1A. In fact my calculations show that on top a heat sink with a thermal resistance of <= 10°C/W, I'll still need a cooling fan given the headroom that my design has. Heatsinking cannot be overemphasized in this design since with all else constant$V_{O}$changes with junction temperature. If you check the graphs of any LM317 datasheet you will find that load regulation, adjustment current, and reference voltage are all temperature dependent. Therefore, keeping the 317 temperature as constant as possible is paramount for a good constant voltage output with a varying load. So there are several reasons for limiting voltage headroom. And one way to do so is to use a multitap transformer and feed the 317 with a voltage that depends on its output. The greater the output voltage the higher the voltage we input to the regulator. A control circuit monitors$V_O$and selects the appropriate transformer tap via electromagnetic relays. Unfortunately, for this design I couldn't find a multiple tap transformer (with four or five outputs) whose maximum voltage output is 30 or so volts RMS. The best I could find is a 14-0-14 volt center-tapped, which is equivalent to a 0-14-28. With only two output voltages only one relay is necessary. The idea is to switch to 28VAC when$V_O$rises above the middle value of around 12VDC and to switch back to 14VAC when it falls below this. A hysteresis band will be necessary to prevent relay "chatter" when crossing the switchover voltage. In my first design I powered the$V_O$monitoring circuit from the same transformer. But it turns out that because the secondary windings are not isolated from one another the voltages go haywire when the two taps are used simultaneously--by the 317 and the monitoring circuit. So I've had to use a second transformer, with 12VAC output, to drive the relay and power the ICs that check$V_{O}$. The monitoring circuit consists simply of a comparator with hysteresis wired in using two positive feedback resistors. I've decided to switch the relay when$V_{O}$is around 13VDC. I will definitely use$V_{O}$= 12VDC so I don't want it switching at that level. And I can't change taps at a much higher voltage since there might not be enough headroom for the regulator when current draw goes above 500mA. So I've pegged the trip comparator trip voltage between 13 and 14VDC. To determine the resistor values, upper and lower trip voltages, and the hysteresis band, I needed formulas. Textbooks have not been of any help. They do have the equations but they're for op amps using bipolar power supplies. I'm keeping to single-supply op amps and those equations simply don't work. I've tried them and results don't match with measured values. Luckily Microchip has the holy grail in their literature. From the Microchip MCP6541 datasheet we have the following equations to determine the trip voltages given positive feedback. $V_{TLH} = V_{REF}\left ( 1 + \frac{ R_{F1}}{R_{F2}} \right ) - V_{OL} \left ( \frac{R_{F1}}{R_{F2}} \right)$ $V_{THL} = V_{REF}\left ( 1 + \frac{ R_{F1}}{R_{F2}} \right ) - V_{OH} \left ( \frac{R_{F1}}{R_{F2}} \right)$ where$V_{TLH}$= trip voltage when voltage at the noninverting input is going from low to high, in volts$V_{THL}$= trip voltage when voltage at the noninverting input is going from high to low, in volts$V_{REF}$= reference voltage, i.e., voltage at the comparator's inverting input, in volts$V_{OL}$= comparator low level output voltag, in volts$V_{OH}$= comparator high level output voltage, in volts${R_{F1}}$,${R_{F2}}$= positive feedback resistances, in ohms If output of the comparator is only very lightly loaded then$V_{OL}$is only a few millivolts above ground. Moreover,${R_{F1}}/{R_{F2}}$is very small. Thus$V_{OL}  ({R_{F1}}/{R_{F2}})$is practically zero.$V_{TLH}$then reduces to: $V_{TLH} = V_{REF}\left ( 1 + \frac{ R_{F1}}{R_{F2}} \right )$ It follows then that $V_{THL} = V_{TLH} - V_{OH} \left ( \frac{R_{F1}}{R_{F2}} \right)$ With a very lightly loaded comparator output,$V_{OH}$is for all practical purposes equal to the comparator's supply voltage$V_{DD}$. Upper and lower trip voltages in terms of$V_O$are obtained as follows: $V_{TLH}' = V_{TLH} \left ( \frac {R_{VD1}+R_{VD2}} {R_{VD2}} \right)$ $V_{THL}' = V_{THL} \left ( \frac {R_{VD1}+R_{VD2}} {R_{VD2}} \right)$ Referring to the schematic above, the comparator's reference voltage is derived from a voltage divider and computed as follows: $V_{REF} = V_{DD} \left ( \frac {R_{REF2}}{R_{REF1} + R_{REF2}} \right)$ where$R_{REF1}$and$R_{REF2}$are the voltage divider resistor values, in ohms The LM317 output voltage$V_O$is to be monitored by the comparator. But because this swings from 1.25 to around 30VDC, while the comparator maximum input voltage is$V_{DD}$= 5VDC, we need to "step down" the voltage sensed by the comparator by using a voltage divider.$ R_{VD1}$and$R_{VD2}$are chosen such that when$V_O$is at its maximum then voltage divider output is equal to the comparator$V_{DD}$. Voltage divider output is given by: $V_O \left ( \frac {R_{VD2}}{R_{VD1}+R_{VD2}} \right)$ The presence of the feedback circuit in the comparator necessitates a low impedance source. The voltage divider formed by$R_{VD1}$and$R_{VD2}$does not meet this requirement. Hence a unity gain buffer is necessary. I initially used a MC33171 op amp for the comparator and a LM310 voltage follower as the buffer. Instead of having two ICs I want to use a dual single supply op amp IC with a$V_{CC}$of > 12VDC but unfortunately I don't have any at hand. But I do have tons of Microchip single, dual, and quad op amps. I picked the MCP6282 for its rail-to-rail input and output and its good slew rate.$R_{VD1}$and$R_{VD2}$were chosen such that the voltage divider's maximum output is 5VDC. Resistors,$V_{DD}$, and$V_{OH}$of the breadboarded prototype were measured using a Fluke 8842A and their values were plugged into the equations above.$V_{TLH}'$and$V_{THL}'$were measured with the multimeter probes connected to$V_O$and ground, and gradually turning the potentiometer. Theoretical and empirical results are within less than 0.25% of each other! That certainly blew my mind. While designing this power supply I used an old malfunctioning ATX power supply 12VDC brushless motor cooling fan as a load since I could turn$V_O$up and down and have some visual feedback on how it's affecting the load. And I could afford to ruin it should it burn up when I turned$V_O$all the way up. Turns out choosing this fan was fortuitous because I discovered something totally unexpected. Without any load the comparator circuit worked fine and, depending on the values of the various resistors, there was some 1.5 to 2V ($V_O$) hysteresis band. But when the fan was powered hysteresis was lost and relay chatter was prominent when the trip voltage level was being crossed. I found out what was happening when I hooked up an oscilloscope to check$V_O$. It showed the fan was introducing positive and negative pulses (see oscilloscope screenshots below). And the comparator circuit was merely following what it's suppose to do--tripping (and being tripped up) when those pulses were present, as the difference between the peak positive and negative values exceeded the hysteresis band set by$R_{F1}$and$R_{F2}$. So I added a low pass filter section whose cutoff frequency can be computed as follows: $f_c = \frac{1}{2\pi R_{LPF}C_{LPF}}$ where$f_c$= filter cutoff frequency, in hertz$R_{LPF}$= filter resistor value, in ohms$C_{LPF}$= filter capacitor value, in farads This circuit filters out any transients occurring in$V_O$. With the LPF circuit in place oscilloscope reading of the unity gain buffer output was devoid of the noise pulses introduced by the fan. I also used a new brushless DC fan as a load. Apparently even brand new fans also introduce spikes into$V_O$although it seems their amplitude is not as high as those of the malfunctioning fan (see screenshots below). But the fans tested are made by different manufacturers so the noise they introduce may be manufacturer specific. Given how the comparator and LPF circuits are working perfectly, I decided to lower the hysteresis band to a 500mV (measured at$V_O$), which translates to around 83mV at the comparator input. With resistor values (I used 5% resistors) provided in the schematic, actual measured upper trip voltage = 13.58V and lower trip voltage = 13.00V. In the Rigol DS1102E oscilloscope screenshots below, channel 1 is set to AC coupling and bandwidth limit is on.$V_O$is set to 12.50V as measured by the Fluke multimeter. All measurements are with respect to circuit ground. Point of measurement: unity gain buffer output Trigger: auto, @296mV Vertical: 200mV/div Horizontal: 5ms/div The used, malfunctioning fan--a Power Logic brushless motor model PL80S12M rated at 12V 0.13A--is powered by$V_O$. There is no low pass filter at the input of the voltage follower. Cursors are on and show that positive peak voltage = 384mVand peak negative voltage= -280mV. The comparator circuit sees these voltage spikes and when$V_O$is at the trip setting the comparator output rapidly alternates between high and low (because the noise is greater than the hysteresis band) resulting in relay chatter. Same screenshot as above but the cursors have been changed to measure time. As can be seen pulses occur every 6.7ms. Point of measurement: unity gain buffer output Trigger: single shot, 120mV Vertical: 200mV/div Horizontal: 2ms/div The lower waveform is a zoomed in display of the portion above that's between the purple bands. Time base for lower display = 50.00µs/div. Same as above but zoomed in portion is that of the spike on the right. Time base is also 50µs/div Point of measurement: unity gain buffer output Trigger: auto, 0.00V Vertical: 200mV/div Horizontal: 5ms/div The same fan is being powered by$V_O$, but now a first order low pass filter with a$f_c$of 16Hz (as per schematic above) is connected to the input of the voltage follower. Voltage spikes have been completely eliminated and the comparator circuit performs flawlessly. Point of measurement:$V_O$Trigger: auto, @2.00V Vertical: 1.00V/div Horizontal: 20.00µs/div This is the first type of pulse from the fan but measured at$V_O$. As can be seen it's the same as that output by the voltage follower without a low pass filter. Point of measurement:$V_O$Trigger: auto, @-1.68V Vertical: 1.00V/div Horizontal: 20.00µs/div This is the second type of pulse but measured at$V_O$. As can be seen it's the same as that output by the voltage follower without a low pass filter. Point of measurement:$V_O$Trigger: auto, @1.08V Vertical: 1.00V/div Horizontal: 20.00µs/div This is the only kind of pulse from a brand new ADDA Brushless DC motor model AD0812MS-A70GL rated at 12V 0.15A. Comparing the pulses, that from the Power Logic has a positive peak that reaches 2.1V while this new fan has a peak of only 1.2V. Negative peak is a bit harder to compare because the ADDA sometimes has negatives spikes that dip to around -2.0V. The most crucial point in all this is that a low pass filter is essential for the$V_O$monitoring circuit to work properly and reliably given various types of loads loads. Backtracking a bit, filter capacitor sizing is important to make sure that ripple voltage at maximum rated current of the power supply is such that there is still enough headroom for the 317 to produce a regulated output. That is, at the comparator trip voltage (switching from lower to higher voltage transformer tap) and at the maximum voltage output of the 317 (~30VDC in this design) the following must hold true: $V_{IN_{no\,load}}- V_{PPripple_{max\,load}} > V_{min\,headroom}$ where$V_{IN_{no\,load}}$= LM317 input voltage with no load at the output, in volts$V_{PPripple_{max\,load}}$= peak-to-peak ripple voltage at the input of the 317 with maximum load connected to its output, in volts$V_{min\,headroom}$= minimum headroom for the voltage regulator, in volts Minimum headroom for the LM317 is around 2.5VDC. To allow enough leeway I peg it at 3V. This headroom requirement is the reason I chose a 14-0-14V over the more common 12-0-12V transformer. Tests with the latter yielded a poor headroom, its output being only 15VDC, rectified and filtered, even at no-load condition. That should in fact be 17.0VDC ($V_{RMS}\sqrt2 $). This problem may be manufacturer related, or I just got a bad batch. The 14-0-14V transformer (made by a different manufacturer) measured 19.6VDC (rectified, filtered, no-load) tapped at its 14VAC output, which is within 1% of the ideal value of 19.8V. Assuming a ripple voltage that's triangular in waveform, the relation between peak-to-peak and RMS values of ripple voltage is given by: $V_{PPripple} = V_{RMSripple}2\sqrt3$ For light loads the following approximation applies: $V_{RMSripple} = \frac {I_{load}}{4\sqrt3 \,fC}$ where$I_{load}$= current draw of the load, in amperes$f$= mains/line frequency, in hertz$C$= capacitance of the filter capacitor, in farads Peak-to-peak ripple is therefore, $V_{PPripple} = \left ( \frac {I_{load}}{4\sqrt3 \,fC} \right ) 2\sqrt3$ $V_{PPripple} = \frac {I_{load}}{2fC}$ With a mains frequency of 60Hz the above simplifies to $V_{PPripple} = \frac {I_{load}}{120C}$ In my design I set a limit of$V_{PPripple}\$ = 1V. Plugging that into the formula yields a capacitor value of 8333µF. I will use either two 4700µF or one 10mF. Cap working voltage should be a minimum of 50V given the 40VAC peak of the transformer.

To adjust the 317's output I'm using is a Bourns 3590S 5Kohm 10-turn precision potentiometer. A high quality pot is necessary to achieve good, reliable, stable resistance and, consequently, voltage output.

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References:

1. LM317 constant voltage reference design with protection diodes and bypass capacitors: STMicroelectonics LM317 datasheet.

2. Equations for power dissipation of LM317 and heatsink requirements: National Semiconductors LM317 datasheet.

3. Single-supply comparator hysteresis equations: Microchip MCP6541 datasheet.

4. Equations for filter capacitor ripple voltage: Electronics Devices and Circuit Theory, 4ed, Robert Boylestad & Louis Nashelsky, 1987,  p.675 and Appendix B.; Nuts and Volts, February 2004, p.11.